Power line carrier transmission apparatus and communication system

ABSTRACT

A power line carrier transmission apparatus for transmitting a transmission symbol via a power line, the power line carrier transmission apparatus including an interleave unit interleaving the transmission symbol, a modulation unit for modulating the transmission symbol interleaved by the interleave unit, and a transmission unit repeatedly transmitting the transmission symbol modulated by the modulation unit M times (where M is an integer larger than 1), wherein M symbols (where M denotes the number of the symbols), which are generated by repeatedly transmitting the transmission symbol M times by the transmission unit, are transmitted without guard intervals being added therebetween.

The present application is a Continuation Application of U.S.application Ser. No. 13/861,320 filed on Apr. 11, 2013, which claimspriority from Japanese Patent Application No. 2012-105866 filed on May7, 2012 the entirety of which is incorporated herein by reference.

BACKGROUND

The present invention relates to power line carrier communicationapparatuses and communication systems, and more particularly to a powerline carrier communication apparatus and a communication system in whichsymbols are transmitted via a power line.

Japanese Unexamined Patent Application Publication No. 2008-172849discloses a power line carrier communication system. The communicationenvironments of power lines are various depending on places and times,and some communication environments may be very poor in terms of theirnoise conditions or impedance conditions. Under such environments, thecommunication standards using the existing OFDM (Orthogonal FrequencyDivision Multiplexing) (such as G3-PLC and PRIME) are inadequate tocarry out favorable communication. Therefore, a robuster communicationmethod is necessary for such environments.

One of the robust communication methods is disclosed in JapaneseUnexamined Patent Application Publication No. 2008-172849. According toJapanese Unexamined Patent Application Publication No. 2008-172849, therobustness of the communication method is retained by redundancy on atime axis. For example, when 80 symbols are to be transmitted, they aretransmitted by being interleaved by 16 types of carrier frequencies(Refer to FIG. 2 and FIG. 3 in the above patent applicationpublication). Specifically, plural symbol sequences are created byreordering transmission symbols on a time axis. Subsequently, pluralinput symbol sequences are modulated by different carrier frequenciesrespectively (Refer to the paragraph 0019 of the above patentapplication publication). Therefore, time-domain repeated signals arecreated at a prestage of frequency interleaving.

SUMMARY

Therefore, it becomes necessary to carry out interleave processing foreach time-domain repeated signal. As a result, there occurs a problem inthat a large amount of data processing is needed.

Other problems of the related arts and new features of the presentinvention will be revealed in accordance with the description about thespecification of the present invention and the accompanying drawingshereinafter.

According to an aspect of the present invention, in a power line carriertransmission apparatus, an interleaved symbol is modulated using an OFDMscheme, and one time-domain OFDM signal is repeatedly transmitted.

According to the aspect of the present invention, a robust communicationcan be carried out with a small amount of data processing.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a block diagram showing the configuration of a power linecarrier communication system according to a first embodiment;

FIG. 2 is a block diagram showing the detailed configurations of ananalog reception circuit and an OFDM demodulation unit both of which areinstalled in a reception apparatus;

FIG. 3 is a block diagram showing the detailed configuration of atime-domain composition unit installed in the reception apparatus;

FIG. 4 is a timing chart schematically showing symbols used in acomposition in a time domain;

FIG. 5 is a block diagram showing a communication system according to acomparative example;

FIG. 6 is a block diagram showing the configuration of a power linecarrier communication system according to a second embodiment;

FIG. 7 is a block diagram showing the configuration of a power linecarrier communication system according to a third embodiment;

FIG. 8 is a block diagram showing the configuration of a power linecarrier communication system according to a fourth embodiment; and

FIG. 9 is a diagram showing the reception symbol timing of a power linecarrier communication system according to the fourth embodiment.

DETAILED DESCRIPTION First Embodiment (Total Configuration of theSystem)

The configuration of a power line carrier communication system accordingto this embodiment (referred to as a communication system hereinafter)will be described with reference to FIG. 1. The communication system 100includes a transmission apparatus 1, a transmission path 20, and areception apparatus 2. The transmission path 20 is, for example, a powerline through which an alternate-current power (AC power) of 50 Hz or 60Hz is transmitted. The transmission apparatus 1 and the receptionapparatus 2 are connected to each other via the transmission path 20.The transmission apparatus 1 outputs a modulated symbol to thetransmission path 20. The reception apparatus 2 receives the symboloutput by the transmission apparatus 1 via the transmission path 20. Inthis way, the transmission apparatus 1 and the reception apparatus 2perform data communication with each other via the transmission path 20.In this case, the communication system 100 performs communication usingan OFDM scheme.

(Transmission Apparatus 1)

The transmission apparatus 1 includes an encoding unit 11, an S/Pconversion unit 12, a frequency/time interleave unit 13, an OFDMmodulation unit 14, a time-domain repeated transmission unit 15, and ananalog transmission circuit 16.

The encoding unit 11 performs encoding processing for encoding atransmission symbol. Here, it will be assumed that the data amount ofthe transmission symbol is N (N is a natural number). For example, theencoding unit 11 adds check bits used for error correction to thetransmission symbol. Therefore, the data amount of the transmissionsymbol is multiplied by R, and the data amount of the transmissionsymbol output from the encoding unit 11 becomes R×N. The S/P conversionunit 12 converts serial data into parallel data. With this conversion,the transmission symbols are converted into parallel data. Subsequently,the S/P conversion unit 12 outputs the transmission symbols, which havebecome the parallel data, to the frequency/time interleave unit 13.

The frequency/time interleave unit 13 interleaves the transmissionsymbol both in a frequency domain and a time domain. In other words, thefrequency/time interleave unit 13 performs both frequency interleavingfor distributing the transmission symbol data in the frequency domainand time interleaving for distributing the transmission symbol data inthe time domain. In the frequency interleaving, the transmission symboldata are assigned to subcarriers of the later-described OFDM modulation.The data amount that is dealt with by the frequency/time interleave unit13 becomes R×N.

The OFDM modulation unit 14 modulates the transmission symbol data,which have been interleaved, with the OFDM scheme. Because the OFDMmodulation uses plural subcarriers (multiple-carriers), the transmissionsymbol data are multiplexed and transmitted in parallel. For example,the OFDM modulation unit 14 maps the transmission symbol data on thesignal points on an IQ plane. Subsequently, an inverse Fourier transformis performed on the mapped transmission symbol data. The OFDM modulationunit 14 converts the interleaved subcarrier data into data on a timeaxis by performing IFFT (Inverse Fast Fourier Transform). In this way,the OFDM modulation unit 14 creates a modulated signal obtained bymodulating the transmission symbol. In addition, the OFDM modulationunit 14 adds a preamble signal to the head of the modulated signal. Thepreamble signal is, for example, a signal obtained by modulatingpredetermined data with the OFDM scheme. Alternatively, the preamblesignal can be a signal other than an OFDM signal (such as a chirpsignal). The data amount that the OFDM modulation unit 14 deals withexcept the preamble becomes R×N.

The time-domain repeated transmission unit 15 repeatedly transmits onemodulated signal obtained by modulating the transmission symbol usingthe OFDM modulation in the OFDM modulation unit 14. For example, thetime-domain repeated transmission unit 15 includes a buffer or the likefor storing a modulated signal corresponding to one symbol. Thetime-domain repeated transmission unit 15 repeatedly transmits themodulated signal stored by the buffer installed in the time-domainrepeated transmission unit 15 at certain fixed time intervals. Here, itwill be assumed that a modulated signal corresponding to onetransmission symbol is repeatedly transmitted M times (M is a numberthat is 2 or larger). In addition, M can be an integer equal to 2 orlarger. In this case, it is possible that guard intervals are notinserted between repeatedly transmitted symbols. The data amount thatthe time-domain repeated transmission unit 15 deals with becomes R×M×N.The modulated signal that is repeatedly transmitted by the time-domainrepeated transmission unit 15 is amplified by an amplifier in the analogtransmission circuit 16, and is output to the transmission path 20. Asdescribed above, the time-domain repeated transmission unit 15repeatedly outputs the same transmission symbol M times to thetransmission path 20.

(Reception Apparatus 2)

Next, the reception apparatus 2 will be described. The receptionapparatus 2 includes an analog reception circuit 21, a time-domaincomposition unit 22, an OFDM demodulation unit 23, a frequency/timedeinterleave unit 24, a P/S conversion unit 25, and a decoding unit 26.

The analog reception unit 21 receives the modulated signal transmittedby the transmission apparatus 1 via the transmission path 20. In thiscase, because an alternate-current power is supplied to the transmissionpath 20, the alternate-current power voltage is superimposed on themodulated signal. The analog reception circuit 21 includes an amplifierthat amplifies the received reception signal with a predefined gain. Thereception signal includes M symbols (where M is the number of symbols)created by the transmission symbol being repeatedly transmitted M timesby the transmission apparatus 1. In addition, the reception signalincludes the preambles added to the heads of the symbols. Subsequently,the analog reception circuit 21 AD-converts the amplified receptionsignal, and outputs the AD-converted signal to the time-domaincomposition unit 22. In addition, the processing performed by the analogreception circuit 21 will be described in detail later.

The time-domain composition unit 22 performs composition in the timedomain using the M symbols created by the transmission symbol beingrepeatedly transmitted M times. For example, the time-domain compositionunit 22 averages the M symbols created by the transmission symbol beingrepeatedly transmitted M times. In other words, the time-domaincomposition unit 22 composes one reception symbol using the M symbolscreated by the transmission symbol being repeatedly transmitted M times.In addition, the processing performed by the time-domain compositionunit 22 will be described in detail later. The M symbols created by thetransmission symbol being repeatedly transmitted M times are convertedinto one reception symbol. Therefore, after the conversion, the dataamount becomes one Mth, and the data amount to be dealt with by the OFDMdemodulation unit 23 in the later stage becomes R×N.

The OFDM demodulation unit 23 demodulates the reception signal of thereception symbol, which is composed in the time domain, with the OFDMscheme. In addition, the processing performed by the OFDM demodulationunit 23 will be described in detail later. The frequency/timedeinterleave unit 24 deinterleaves the reception symbol included in thereception signal demodulated with the OFDM scheme. The frequency/timedeinterleave unit 24 performs deinterleaving in the reverse order of theinterleaving performed by the frequency/time interleave unit 13. Withthis deinterleaving, the data distributed both in the frequency domainand the time domain are put back into their original places. The dataamount that the frequency/time deinterleave unit 24 deals with becomesR×N.

The P/S conversion unit 25 converts the parallel data of the receptionsymbol deinterleaved by the frequency/time deinterleave unit 24 intoserial data. The P/S conversion unit outputs the reception symbol thatis converted into the serial data to the decoding unit 26. Subsequently,the decoding unit 26 decodes the data of the reception symbol that areconverted into the serial data. The decoding unit 26 decodes the data ofthe reception symbol in the reverse order of the encoding performed bythe encoding unit 11. With this decoding, the data amount of thereception symbol gets back from R×N to N.

Next, the processing performed by the analog reception circuit and theprocessing performed by the OFDM demodulation unit 23 will be describedin detail with reference to FIG. 2. FIG. 2 is a block diagram showingthe configuration examples of the analog reception circuit 21 and theOFDM demodulation unit 23.

(Analog Reception Circuit 21)

First, the configuration of the analog reception circuit 21 will bedescribed. The analog reception circuit 21 includes a coupler 44, areceiving amplifier 41, an ADC (Analog Digital Converter) 42, and anacquisition AGC (Automatic Gain Control) synchronization unit 43.

The coupler 44 is coupled with the transmission path 20, and receives areception signal that propagates through the transmission path 20. Next,the coupler 44 outputs the reception signal to the receiving filter 45.The coupler 44 and the receiving filter 45 separate the OFDM signal andthe alternate-current power. The receiving amplifier 41 receives thereception signal, which propagates through the transmission path 20, viathe coupler 44 and the receiving filter 45, and amplifies the receptionsignal with a predefined gain. The ADC 42 creates a digital receptionsignal by AD-converting the reception signal amplified by the receivingamplifier 41. The acquisition AGC synchronization unit 43 adjusts thegain of the receiving amplifier 41. For example, on detecting a preamblepredetermined, the acquisition AGC synchronization unit 43 adjusts thereceiving gain in accordance with the input level to the ADC 42 on thebasis of the digital reception signal obtained after the AD-conversion.In other words, on detecting a preamble signal corresponding to thepreamble, the acquisition AGC synchronization unit 43 adjusts the gainof the receiving amplifier 41.

In addition, the acquisition AGC synchronization unit 43 establishesframe synchronization by detecting borders among preamble signals andpayloads. The acquisition AGC synchronization unit 43 notifies thetime-domain composition unit 22 and an FFT unit 27 of the OFDMdemodulation unit 23 of this timing for the frame synchronization. Owingto the above notification, the time-domain composition unit 22 and theOFDM demodulation unit 23 can work in synchronization with each other.For example, on detecting the preamble from the reception signalobtained after the AD-conversion, the acquisition AGC synchronizationunit 43 adjusts the timing of processing performed by the time-domaincomposition unit 22 in accordance with the detected timing of thepreamble. With this adjustment, the symbol borders of the repeatedsymbols are determined. Subsequently, the time-domain composition unit22 performs time-domain composition using the M symbols which arecreated by the transmission symbol with a predefined symbol length beingrepeatedly transmitted M times. In a similar way to the above, theacquisition AGC synchronization unit 43 controls the processingperformed by the FFT unit 27 in accordance with the detected timing ofthe preamble.

(OFDM Demodulation Unit 23)

The OFDM demodulation unit 23 includes the FFT unit 27 thatFourier-transforms the reception symbol and a demapping unit 28 thatperforms demapping. For example, the FFT unit 27 performs FFT (FastFourier Transform) on the data of the reception symbol composed by thetime-domain composition unit 22 to transform the data of the receptionsymbol into complex data in the frequency domain. Next, thefrequency-domain complex data are demodulated through points, which aredepicted by the frequency-domain complex data, on the complex planebeing demapped by the demapping unit 28, with the result that the dataof the reception symbol are retrieved. In addition, the timing ofprocessing performed by the FFT unit 27 is controlled by the acquisitionAGC synchronization unit 43. With the above control, the FFT can beperformed with an appropriate timing on one reception symbol composed bythe time-domain composition unit 22. Subsequently, the data of thereception symbol obtained after the demapping are output to thefrequency/time deinterleave unit 24.

(Time-Domain Composition Unit 22)

Next, the processing performed by the time-domain composition unit 22will be described with reference to FIG. 3 and FIG. 4. FIG. 3 is a blockdiagram showing an example of the configuration of the time-domaincomposition unit 22. FIG. 4 is a timing chart showing processing inwhich composition is performed in a time domain using symbols and areception symbol is created. FIG. 4 shows an example in which onetransmission symbol is repeatedly transmitted four times.

The time-domain composition unit 22 includes a symbol waveformcomposition unit 31 and a noise detection unit 32. The symbol waveformcomposition unit 31 averages the M symbols created by the transmissionsymbol being repeatedly transmitted M times. For example, as shown inFIG. 4, it will be assumed that the first group of four symbols, whichare created by the transmission symbol being repeatedly transmitted fourtimes, includes symbols S1-1, S1-2, S1-3, and S1-4. In a similar way, itwill be assumed that the second group of four symbols, which are createdby the transmission symbol being repeatedly transmitted four times,includes symbols S2-1, S2-2, S2-3, and S2-4. For example, the symbolsS1-1, S1-2, S1-3, and S1-4, and the symbols S2-1, S2-2, S2-3, and S2-4have the same symbol lengths, and they are continuously transmitted.

The symbol waveform composition unit 31 outputs a composited symbolwaveform to the OFDM demodulation unit 23. Although there may be variouscomposition methods, it will be assumed in this case that a method inwhich the symbol waveform composition unit 31 averages the symbols S1-1to S1-4 is adopted. A preamble is added to the head of the first symbolS1-1. As described above, the symbol waveform composition unit 31averages the symbols S1-1 to S1-4 in accordance with the timing ofdetection of the preamble by the acquisition AGC synchronization unit43. In other words, since the acquisition AGC synchronization unit 43has already detected the preamble, the symbol waveform composition unit31 can detect borders between the symbols S1-1 to S1-4. Owing to thisdetection, the symbol waveform composition unit 31 can average thesymbols S1-1 to S1-4 to compose a reception symbol R1. In this way, thesymbol waveform composition unit 31 composes one reception symbol R1 byaveraging the four symbols S1-1 to S1-4 created by the transmissionsymbol being repeatedly transmitted M times (in this example, M =4).

Here, although the symbols S1-1 to S1-4 have the same signal waveformsat the transmission apparatus 1 side, these symbols have differentsignal waveforms at the side of the reception apparatus 2 owing to thecommunication environment including the transmission path 20 and thelike. For example, if a noise is generated on the transmission path 20,the analog reception circuit 21 receives a reception signal having asymbol on which the noise is superimposed.

In the case where a noise is superimposed on a symbol, there is fearthat the data of the reception symbol obtained by demodulating symbolsis not correct. Therefore, in this embodiment, the noise detection unit32 detects a noise generated in the transmission path 20. The noisedetection unit 32 outputs the noise detection result to the symbolwaveform composition unit 31. Subsequently, the symbol waveformcomposition unit 31 performs composition using the symbols except asymbol obtained at the timing of the noise detection.

For example, as shown in FIG. 4, it will be assumed that a noise isgenerated in the symbol S2-2 of the symbols S2-1 to S2-4. In this case,the symbol waveform composition unit 31 averages the symbol S2-1, thesymbol S2-3, and the symbol S2-4 except the symbol S2-2. In other words,the symbol waveform composition unit 31 calculates a reception symbol R2by averaging the above three symbols. In general, the symbol waveformcomposition unit 31 averages the symbols except some symbols of Msymbols created by the transmission symbol being repeatedly transmittedM times (M=4 in this case) in the time domain. Subsequently, asdescribed above, the calculated reception symbol by averaging isOFDM-demodulated by the OFDM demodulation unit 23.

For example, the noise detection unit 32 calculates the power of eachsymbol. If a noise is mixed in a symbol, the power of the symbol becomeslarger. Therefore, if the noise detection unit 32 receives a symbolwhose power is equal to a certain threshold or larger, the noisedetection unit 32 judges that a noise is mixed in the symbol. The noisedetection unit 32 informs the symbol waveform composition unit 31 of thenoise detection result. The symbol waveform composition unit 31 averagesthe symbols except the symbol S2-2 in which the noise is mixed. Thesymbol waveform composition unit 31 performs composition using thesymbols except the symbol S2-2 among the M symbols because the power ofthe reception signal of the symbol S2-2 exceeds the threshold of the Msymbols. In such a way, the adverse effect of a suddenly generated noisecan be reduced.

Alternatively, it is also conceivable that the time-domain compositionunit 22, in which no noise detection unit is installed, performscomposition using the M symbols created by the transmission symbol beingrepeatedly transmitted M times regardless of the presence or absence ofnoises. In other words, regardless of the presence or absence of anoise, all the M symbols created by the transmission symbol beingrepeatedly transmitted M times can be averaged. In addition, it is alsoconceivable that the time-domain composition unit 22 performscomposition using the M symbols through a maximum ratio combining methodor the like.

In addition, after the transmission symbol is interleaved andOFDM-modulated, the time-domain repeated transmission unit 15 repeatedlytransmits the transmission symbol M times. With the above procedures,the amount of processing dealt with by the frequency/time interleaveunit 13 and the OFDM modulation unit 14 can be reduced. In other words,because the amount of data processing dealt with by the FFT and theinterleaving can be reduced, the total amount of data processing can bereduced. Therefore, a processing time can be shortened.

For example, as shown by a comparative example in FIG. 5, it will beassumed that encoding, S/P conversion, time-domain repeatedtransmission, frequency interleaving, and OFDM modulation are performedon a transmission symbol with a data amount N in this order. If the dataamount is multiplied by R in the encoding, and the transmission symbolis repeatedly transmitted M times in the time domain, the data amountdealt with by the frequency interleaving and by the OFDM modulationbecomes R×M×N. Therefore, the data amount dealt with by thefrequency/time interleave unit 13 and by the OFDM modulation unit 14becomes M times the data amount dealt with in FIG. 1. In a similar way,in the reception apparatus 2, the data amount dealt with by the OFDMdemodulation unit 23 and by the frequency/time deinterleave unit 24becomes M times the data amount dealt with in FIG. 1. This means theamount of the OFDM modulation and demodulation processing andinterleaving and deinterleaving processing become M times the dataamount dealt with by the OFDM modulation in FIG. 1.

On the other hand, in the configuration shown in FIG. 1, the data amountdealt with by the OFDM demodulation unit 23 and the frequency/timedeinterleave unit 24 can be reduced. In addition, the time-domainrepeated transmission unit 15 has only to repeatedly transmit the samesymbol that is stored in the buffer or the like. Therefore, acalculation for the repeated transmission becomes unnecessary, whichleads to simplification of the repeated transmission processing. Inaddition, in FIG. 1, the reception apparatus 2 performs the OFDMdemodulation and the deinterleaving after the composition by thetime-domain composition unit 22. Therefore, in FIG. 1, it is alsopossible to reduce the data amount dealt with by the OFDM demodulationunit 24 and by the frequency/time deinterleave unit 24 in the receptionapparatus 2. As described above, a robust communication using a smalldata amount can be realized according to this embodiment of the presentinvention.

In this embodiment, it becomes possible not to insert guard intervalsbetween the symbols as shown in FIG. 4. In other words, the last symbolS1-4 of the first group of symbols and the first symbol S2-1 of thesecond group of symbols are continuously transmitted. The symbols S-1 toS1-4 are created on the basis of the same transmission symbol.Therefore, under a condition in which there is no noise, the symbolsS1-1 to S1-4 are received as almost the same signals. In a similar way,the symbols S2-1 to S2-4 are received as almost the same signals underthe same condition.

In addition, a part of the symbols created by the transmission symbolbeing repeatedly transmitted can be used as a guard interval. To put itconcretely, a beginning part or an ending part of the M symbols createdby the transmission symbol being repeatedly transmitted M times can beused as a guard interval. By using the beginning part or ending part ofthe M symbols as a guard interval, the deterioration of demodulationcharacteristic owing to multipaths can be suppressed. In addition,because there is no guard intervals between the M symbols, the receptionsignal can be effectively utilized, which leads to the improvement ofthe reception characteristic of the reception apparatus according tothis embodiment. In addition, compared with a general OFDM modulationscheme in which a guard interval is added to each symbol, the OFDMmodulation scheme according to this embodiment can more effectivelyprevent the deterioration of transmission rate.

On the other hand, in the configuration of the comparative example shownin FIG. 5, symbols are interleaved after being created by thetransmission symbol being repeatedly transmitted in a time domain.Therefore, the symbols that are continuously transmitted are differentfrom each other. As a result, it is necessary to insert guard intervalsbetween the symbols transmitted by a general OFDM modulation scheme.Owing to the guard intervals being inserted between the symbols, thetransmission rate of the comparative example is lower than that of thisembodiment.

Second Embodiment

A communication system 102 according to this embodiment will bedescribed with reference to FIG. 6. In this embodiment, the dispositionorder of an OFDM demodulation unit 23 and a time-domain composition unit22 is opposite to that of the first embodiment. The dispositions ofother units other than the OFDM demodulation unit 23 and the time-domaincomposition unit 22 are the same as those of the first embodiment,explanation about the other units of this embodiment will be omitted.

In the second embodiment, after the OFDM demodulation unit 23OFDM-demodulates the symbols, the time-domain composition unit 22performs composition using these symbols. In other words, after FFT anddemapping are performed on the symbols by the OFDM demodulation unit 23,the time-domain composition unit 22 performs composition using thesesymbols. Subsequently, a reception symbol composed by the time-domaincomposition unit 22 is deinterleaved by a frequency/time deinterleaveunit 24. Therefore, the data amount dealt with by the frequency/timedeinterleave unit 24 becomes R×N.

With above-described configuration, it is also possible to decrease thedata amount dealt with by the frequency/time deinterleave unit 24. Inaddition, the configuration shown in FIG. 6 is effective in the casewhere the number of subcarriers is small with respect to an FFT size ofthe FFT. For example, there is a case where, after being transformed ina frequency domain by the FFT, the symbols are mapped without using apart of the frequency band. For example, there is a case where thesymbols are mapped using only a hundred subcarriers out of five hundredsubcarriers. In such a case, the data amount can be effectively reduced.According to this embodiment, a robust communication using a small dataamount can be realized.

Here, the time-domain composition unit 22 calculates the average valuesof coordinates on an IQ plane. Specifically, the OFDM demodulator unit23 calculates the coordinates of symbols S1-1 to S1-4 on the IQ plane.Subsequently, the time-domain composition unit 22 calculates theposition of the reception symbol on the IQ plane using the averagevalues of the coordinates of the symbols S1-1 to S1-4. With such acalculation, the reception symbol can be easily composed in the timedomain.

In addition, as is the case of the first embodiment, it is conceivablethat the symbols used for averaging are decided on the basis of a noisedetection result. In other words, it is conceivable that a symboltransmitted at a timing when there is a large noise is not used for theaveraging. It goes without saying that the symbols can be averagedregardless of the presence or absence of noises.

Third Embodiment

The OFDM demodulation unit 23 according to the first embodiment includesthe FFT unit 27 and the demapping unit 28 in a disposition order asshown in FIG. 2. In this embodiment, an FFT unit 27, a time-domaincomposition unit 22, and a demapping unit 28 are deposited as shown inFIG. 7. In other words, after the FFT unit 23 performs FFT processing,the time-domain composition unit 22 performs composition in a timedomain. In addition, after the composition performed in the time domainby the time-domain composition 22, the demapping unit 28 performsdemapping.

The time-domain composition 22 composes a reception symbol by averagingdata of symbols in units of frequencies. For example, the FFT unit 27performs the FFT on each of symbols S1-1 to S1-4. The time-domaincomposition 22 averages the frequency-domain data of the symbols S1-1 toS1-4 on which the FFT has already performed. By the above averaging, thefrequency-domain data of the reception symbol is calculated.Subsequently, the demapping unit 28 performs demapping on receptionsymbol on the basis of the averaged frequency data.

Even with such a configuration, the data amount dealt with by afrequency/time deinterleave unit 24 can be reduced as is the case of thesecond embodiment. In addition, it is also possible to make the dataamount dealt with the demapping unit 28 R×N. In addition, theconfiguration shown in FIG. 7 is effective in the case where the numberof subcarriers is small with respect to an FFT size of the FFT. Forexample, there is a case where, after being transformed in a frequencydomain by the FFT, the symbols are mapped without using a part of thefrequency band. For example, there is a case where the symbols aremapped using only a hundred subcarriers out of five hundred subcarriers.In such a case, the data amount can be effectively reduced. Therefore, arobust communication using a small data amount can be realized accordingto this embodiment. In addition, in this third embodiment as is the caseof the first embodiment, it is conceivable that the symbols used foraveraging are decided on the basis of a noise detection result. In otherwords, it is conceivable that a symbol transmitted at a timing whenthere is a large noise is not used for the averaging. It goes withoutsaying that the symbols can be averaged regardless of the presence orabsence of noises.

Fourth Embodiment

A communication system 104 according to this embodiment will bedescribed with reference to FIG. 8. FIG. 8 is a block diagram showingthe configuration of the communication system according to thisembodiment. In addition to the configuration of the second embodiment,the communication system 104 according to this embodiment includes azero-cross detection unit 51, a zero-cross detection unit 52, and atransmission path profile measurement unit 53. Here, because theconfigurations of units other than the zero-cross detection unit 51, thezero-cross detection unit 52, and the transmission path profilemeasurement unit 53 are the same as those included in the firstembodiment or in the second embodiment, the explanation about those unitwill be omitted.

A transmission apparatus 1 d includes the zero-cross detection unit 51.The zero-cross detection unit 51 detects the phase of analternate-current power on the basis of the zero-cross points of thealternate-current power that is transmitted through a transmission path20. Subsequently, the zero-cross detection unit 51 outputs the detectedphase to a time-domain repeated transmission unit 15.

The time-domain repeated transmission unit 15 controls the timing atwhich a transmission symbol is repeatedly transmitted on the basis ofthe phase detected by the zero-cross detection unit 51. For example, thetime-domain repeated transmission unit 15 sets the repeated transmissionperiod of the transmission symbol to be K times (where K is a naturalnumber) the half-period of the alternate-current power. In other words,the repeated transmission period of the transmission symbol is K/2 timesthe period of the alternate-current power on the transmission path 20.The repeated transmission period of the transmission symbol is a timeneeded for the transmission symbol to be repeatedly transmitted M times,and does not includes a time needed for preambles or the like. In theabove described example, the repeated transmission period becomes Mtimes the symbol length of the symbol S1-1. Alternatively, thezero-cross detection unit 51 included in the transmission unit 1 d canbe replaced with a timer or the like for detecting the phase of thealternate-current power.

Here, it will be assumed that one period of the transmission symbol is atime for one transmission of M-times transmissions of the transmissionsymbol. In other words, one period of the transmission symbol is one Mthof the repeated transmission period. In the above described example, oneperiod of the transmission symbol becomes the symbol length of thesymbol S1-1. If the period of the alternate-current power is not anintegral multiple of one period of the transmission symbol, the lastsymbol runs off the period of the alternate-current power. In this case,it will be assumed that a front part of the data of the last symbol isadopted. In other words, the symbol length of the last symbol of symbolscreated by the reception signal being transmitted M times is madeshorter than other symbols. By shortening the symbol length of the lastsymbol, the timing at witch the last symbol ends can be matched with theperiod of the alternate-current power. As an alternative, the symbollength of the first symbol can be shortened in stead of the symbollength of the last symbol. In this way, the time-domain repeatedtransmission unit 15 adjusts the repeated transmission period of thetransmission symbol and one period of the transmission symbol on thebasis of the period of the alternate-current power.

A reception apparatus 2 d includes the zero-cross detection unit 52 andthe transmission path profile measurement unit 53. The zero-crossdetection unit 52 detects the phase of the alternate-current power thatis transmitted through a transmission path 20 as is the case of thezero-cross detection unit 51. Subsequently, the zero-cross detectionunit 52 outputs the detected phase to the transmission path profilemeasurement unit 53.

The transmission path profile measurement unit 53 measures the profileof the transmission path 20. The transmission path profile measurementunit 53 measures the profile of the transmission path 20 that varies ina cycle of the half period of the alternate-current power in advancebefore receiving a frame. The transmission path profile measurement unit53 determines symbol borders between the symbols created by thereception symbol being repeatedly transmitted on the basis of themeasured transmission path profile. Subsequently, a time-domaincomposition unit 22 and an OFDM demodulation unit 23 perform their ownprocessing on the basis of the symbol borders determined by thetransmission path profile measurement unit 53. In other words, the OFDMdemodulation and the composition are performed at the symbol bordersdetermined by the transmission path profile measurement unit 53.

One example of the profile measurement methods is a method in which thevariation of noise amounts is estimated using the average value of theabsolute values of reception signals measured during times where anysignals are not really transmitted in the half-period of thealternative-current power. As a time-domain composition method, amaximum ratio combining method can be conceivable in which a SNR(Signal-to-Noise Ratio) of each symbol estimated from the result of thetransmission path profile measurement is utilized. In this method,because symbols corresponding to bad transmission path profiles havedeteriorated SNRs, they have low weights.

The transmission path profile measurement unit 53 installed in thereception apparatus makes it possible for the OFDM demodulation unit 23to adjust the symbol borders of the reception signals so as to bematched with the corresponding transmission path profiles. Therefore, anumber of symbols that have less degradations can be received, whichleads to the improvement of the reception characteristic. For example,noises on the transmission path 20 are often generated at certain phasesof the alternate-current power on a power line. Therefore, the receptioncharacteristic can be improved by determining the symbol borders on thebasis of the transmission path profile.

For example, it will be assumed that, as shown in FIG. 9, noises aregenerated at certain phases of the alternate-current power on thetransmission path 20. At the timings of generations of noises, thedemodulation characteristics of the symbols are deteriorated. In anexample shown in FIG. 9, noises are generated in a cycle of a phase 180°of the alternate-current power. FIG. 9 shows that a noise is generatedaround the border between the symbol S1-4 and the symbol S2-1. Theperiod of the noise generation straddles two symbols S1-4 and S2-1. In asimilar way, a noise is generated around the border between the symbolS2-4 and the symbol S3-1. Therefore, the noises are superimposedrespectively on two symbols S2-1 and S2-4 of four symbols S2-1 to S2-4created by the transmission symbol being transmitted four times. Inother words, the four symbols 52-1 to S2-4 created by the transmissionsymbol being transmitted four times includes the symbol S2-2 and thesymbol S2-3 that are corresponding to good transmission path profilesand the symbol S2-1 and the symbol S2-4 that are corresponding to badtransmission profiles. Therefore, of the four symbols created by thetransmission symbol being transmitted four times, there are only twosymbols that are corresponding to good profiles of the transmission path20. When a noise detection unit 32 detects the noises, a symbol waveformcomposition unit 31 does not use the symbol S2-1 and the symbol S2-4 foraveraging.

Therefore, in this embodiment, the symbol borders are determined so asto reduce the number of symbols that are corresponding to bad profilesof the transmission path 20. FIG. 9 shows a symbol Sa1-1 to a symbolSa3-3 which have symbol borders determined by the reception processingof the reception apparatus 2 d. The symbol borders are determined sothat the symbol Sa2-1 covers a period of noise generation. In otherwords, the transmission path profile measurement unit 53 determines thesymbol borders so that a period of noise generation does not straddleplural symbols. In this case, although a noise is superimposed on thesymbol Sa2-4, the noise is not superimposed on any of the symbol Sa2-1to the symbol Sa2-3. Therefore, of the four symbols created by thetransmission symbol being transmitted four times, there are threesymbols that are corresponding to good profiles of the transmission path20. In other words, demodulation can be performed using the threesymbols corresponding to good profiles of the transmission path 20,which leads to the improvement of the reception characteristic.

In the above-described way, when the frame is received, the symbolborders are determined on the basis of the result of the transmissionpath profile measurement. In this case, while symbols corresponding tobad profiles of the transmission path are discarded, the phase of thealternate-current power is determined so that the number of symbolscorresponding to good profiles becomes as large as possible. In otherwords, the symbol borders are determined so that the number of symbolsto be discarded becomes as small as possible. In this case, it is notnecessary for the symbol borders to coincide with the symbol borders setin the transmission apparatus side. The reason is that the symbols arethe same because they are created by the same transmission symbol beingrepeatedly transmitted, and the transmission method in which guardintervals are not used between the symbols is adopted. Therefore, thereception characteristic can be easily improved. In addition, the symbolS1-1 to the symbol S1-4 are created on the basis of the sametransmission symbol. Therefore, even if the symbol borders of thereception signals are determined at the side of the reception apparatus2 d independently of the transmission apparatus 1 d side, thedeterioration of the reception characteristic can be prevented.

Although, in this fourth embodiment, the profile measurement function isadded to the second embodiment, the profile measurement function can beadded to the first embodiment or to the third embodiment. In addition,in the fourth embodiment, it is conceivable that averaging can beperformed regardless of the presence or absence of a noise.Alternatively, it is also conceivable that another composition methodsuch as a maximum ratio combining method is adopted instead of theaveraging. In addition, it is also conceivable that some of the firstembodiment to the fourth embodiment are appropriately combined.

Although the present invention achieved by the inventors has beenconcretely described on the basis of some embodiments, the presentinvention is not limited to the above-described embodiments, and it goeswithout saying that various modifications may be made to theabove-described embodiments without departing from the spirit and scopeof the present invention.

What it claimed is:
 1. A power line carrier transmission apparatus fortransmitting a transmission symbol via a power line, the power linecarrier transmission apparatus comprising: an interleave unitinterleaving the transmission symbol; a modulation unit for modulatingthe transmission symbol interleaved by the interleave unit; and atransmission unit repeatedly transmitting the transmission symbolmodulated by the modulation unit M times (where M is an integer greaterthan 1), wherein M symbols (where M denotes the number of the symbols),which are generated by repeatedly transmitting the transmission symbol Mtimes by the transmission unit, are transmitted without guard intervalsbeing added therebetween.
 2. The power line carrier transmissionapparatus according to claim 1, wherein the modulation unit modulatesthe transmission symbol interleaved by the interleave unit with an OFDM(Orthogonal Frequency Division Multiplexing) scheme.
 3. The power linecarrier transmission apparatus according to claim 1, wherein themodulation unit multiplexes data of the transmission symbol in parallelby using assigned subcarriers in the interleave unit.
 4. The power linecarrier transmission apparatus according to claim 1, further comprises adetector detecting the phase of the alternate-current power of the powerline, wherein the transmission unit adjusts the repeated transmissionperiod of the transmission symbol and one period of the repeatedtransmission symbol based on the period of an alternate-current power onthe power line.
 5. The power line carrier transmission apparatusaccording to claim 4, wherein the period of the repeated transmission isK/2 (where K is a natural number) times the period of thealternate-current power.
 6. The power line carrier transmissionapparatus according to claim 1, wherein the transmission unit repeatedlytransmits a same transmission symbols that is stored in a buffer.